EMC Design Guidelines
These Electromagnetic Compatibility (EMC) design guidelines are here to help you to understand the basics on how to make a good EMC PCB design or EMC cabling design. Good in this context means: with low Electromagnetic Interference (EMI).
Following these guidelines helped many engineers to succeed in EMC testing of several products. However, be aware that guidelines alone cannot do magical things to your design. Be wary! However, getting the basics right will reduce the pain of EMC testing and increases the chances of right-first-time. And that is all that we want, right?
Table Of Content
The preface to the guidelines:
Preface – GND planes and signal return reference planes.
Fundamental EMC design guidelines for PCB design:
Guideline #1 – Never route signals over split reference planes!
Guideline #2 – Keep current loops as small as possible.
Guideline #3 – Decoupling: use low-inductance capacitors/traces AND planes.
Guideline #4 – Use ground planes on PCB for shielding.
Guideline #5 – Route high-frequency signals adjusted to a plane.
Guideline #6 – Control rise- and fall-time.
Guideline #7 – Add ceramic capacitors close to every pin of a connector.
Guideline #8 – Fill top and bottom layer with circuit GND and matelize the PCB edges.
Guideline #9 – Add stitching vias around high-speed signal vias.
Guideline #10 – Connect circuit GND to chassis at IO area.
Fundamental EMC design guidelines for cabling and wiring:
Guideline #11 – Lay cables along chassis (GND/earth).
Guideline #12 – Do NOT use shield as signal conductor for low-frequency signals.
Guideline #13 – Lay only one end of the cable shield to ground for low-frequency signals.
Guideline #14 – Lay both ends of the cable shield to ground for high-frequency signals.
Guideline #15 – Minimize loop area of signals in cables.
We try to avoid the terms ground plane and GND plane in our guidelines. Whenever appropriate, we use the terms signal return plane or return signal reference plane or simply: reference plane. Why this?
Currents flow in loops. A current does always return to its source. And a common issue is that engineers tend to forget about this when they design PCBs and electronics systems, especially when they design digital systems where you can only see the signal traces from chip to chip and the return current flows through the "GND symbols" in the schematic. The majority of EMC problems (e.g. radiated emission, ESD) involve high-frequency signals (several megahertz - MHz). It is important to understand that a return current of a signal above about 50kHz prefers to flow close to the forward current, e.g. directly under the forward current in an adjusted power supply or ground plane - the so called return signal reference plane.
The following two impressive images compare the return currents through a reference plane of a low-frequency signal vs. a high-frequency signal (source: EMI Troubleshooting Cookbook for Product Designers). In the left picture, the signal has a frequency of 1kHz and in the right 1MHz. The difference is obvious and eye-opening! So lets get started with the guidelines and learn more about EMC compliant design.
EMC Guideline # 1 – Never route signals over split reference planes!
Lower radiated emission
Do not route signals over split return signal reference planes (GND, power planes)! Never! This leads to unnecessary large current loops (as the current return cannot flow directly under/beside the forward current) and large current loops in general lead to high radiated emission values.
Rule Of Thumb #1: Whenever in doubt, do not split return current reference planes (GND, power planes), go with a solid filled reference plane instead. There must be a good reasons for splitting planes! There should always be at least one solid reference plane closely adjusted to signals.
EMC Guideline #2 – Keep current loops as small as possible.
Lower radiated emission
Always consider the return current! Always! And with the return current in mind: minimize the loop you have between forward and return current. This is especially true for high-frequency signals (several MHz), in other words: clocks! As Henry W. Ott said: “Get paranoid about clocks!”.
This is a very generic guideline and should always be kept in mind. Out of this guideline, many others will follow here in a more specific way.
Hint #1: We assume that you have a high-frequency signal (s1, >1MHz) trace on layer 1 and a reference plane (e.g. GND or power plane) on the neighbor layer 2, the return current of the high-frequency signal (s1) on the reference plane prefers to flow directly under the trace of s1. Read more details in this book here or the preface of these guidelines.
EMC Guideline #3 – Decoupling: use low-inductance capacitors / traces AND planes.
Lower radiated emission, lower impedance coupling
Decoupling is important! Always consider decoupling! Place ceramic capacitors close to EVERY power supply pin of EVERY chip on your PCB design.
Decoupling depending on PCB stackups:
Multilayer PCB: Design a PCB stackup with power supply plane and GND plane close together (<0.1 mm or 2...3 mils). This leads to an especially good decoupling at high frequencies (>1MHz).
Double/single layer PCB: Keep traces of decoupling capacitors to power-supply-pin and ground-pin as short as possible (to keep inductance as low as possible).
EMC Guideline #4 – Use ground planes on PCB for shielding.
Lower on-board interferences
Use solid filled reference planes (e.g. GND or power supply planes) on a PCB to separate noisy signals (e.g. motor signals) from sensitive signals (e.g. sensor signals). The reference plane will act as a shield and will lower Electromagnetic Interference (EMI). Be aware, that the shielding of such a copper plane will primarily be effective for E-fields and not H-field, because copper has a low μr and does not shield against (low-frequency) magnetic fields. Read more about shielding in our Knowledge Database.
EMC Guideline #5 – Route high-frequency signals adjusted to a plane.
Lower radiated emission
This guideline follows out of EMC Guideline #1 and EMC Guideline #2: route high-frequency signals (>50kHz) ALWAYS closely to an adjusted reference plane (GND or power supply plane, which acts in this case as a high-frequency ground). For single layer designs: use guard traces close to the high-frequency signal where the return current can flow.
Hint #3: Generally core laminate is more reproducible than prepreg regarding thickness and dielectric constant. This means that controlled impedance layers should ideally be routed along the core material, rather than prepreg. Read more about PCB layer stackup in our Knowledge Database.
EMC Guideline #6 – Control rise and fall time.
Lower radiated emission
Lower rise- and fall time of any digital signal (especially clock signals) as far as possible.
Rule Of Thumb #2: Add a series resistor (typically 33 Ohm, close to the driver's output) to all digital signal traces with signal length [inch] higher than rise-/fall-time [nsec].
Rule Of Thumb #3: The approximately highest frequency content in a digital signal depends NOT on the first harmonic (fundamental frequency), it depends on the rise/fall-time:
Where t10%-90% is the rising- or fall-time from 10% to 90% of the slope of a digital signal in [sec] and fknee is the maximum frequency content in [Hz].
Example: Given a digital clock with rise/fall-time of t10%-90%=1nsec which runs over a PCB microstrip trace which has a length of 250mm (10inch). The highest frequency content in this digital signal is approximately fmax=fknee≈350MHz and has a wavelength of λ≈v/fknee=500mm, where v is the propagation velocity of the electromagnetic wave inside the signal PCB media and air (typical dielectric constant εr=4.5 for FR-4 and an effective dielectric constant of εreff≈3.0 for the assumed microstrip line):
The digital clock signal with a rise/fall-time of 1nsec running through a trace on a PCB with FR-4 material results in λ/2=250mm and λ/10=50mm for fmax. Given all these facts, the PCB trace of length 250mm will tend to radiate at high levels (because a trace length or cable of length λ/2 makes a good antenna). To prevent this: add a series resistor close to the drivers output which will lower the rise/fall-time.
Rule Of Thumb #4: Every PCB trace of length longer than λ/10 should be considered as a transmission line and no longer as a simple interconnection. This means that such a trace should be laid out with controlled impedance. In other words: there should not be any impedance changes / discontinuities along the PCB trace, as these impedance changes / discontinuities lead to e.g. reflections. Reflections affect the signal integrity (not the topic here) and lead to electromagnetic radiation. Read more details in this book here.
EMC Guideline #7 – Add ceramic capacitors close to every pin of a connector.
ESD, lower radiated emission, increase radiated immunity
Filtering of signals directly at the connector is very important! This helps to add Electrostatic Discharge (ESD) immunity to your PCB, lower radiated emission and increase immunity to coupled burst signals on IO cables.
Every signal or power supply line which enters or leaves your PCB needs a ceramic capacitor. One side of the capacitor close to the connector pin, the other pin tied to the ground plane. Some rules of thumb:
Hint #4: Signals which go outside your device (e.g. a connector which people can touch with their hands), will be tested with an ESD gun (±2kV, ±4kV, ±6kV, ±8kV). In this case, use capacitors with high voltage rating (e.g. >250V, depending on capacitance and ESD test voltage and other components involved, e.g. like ferrite beads between connector pin and capacitor).
EMC Guideline #8 – Fill top and bottom layers with circuit GND and metalize the PCB edges.
Lower radiated emission
Fill top and bottom layers of a PCB with a solid ground plane around the signals (copper area) and metalize the PCB edges. This helps to minimize radiated emission, because the filled GND areas at top and bottom help to shield inner-layer signals from radiation. Moreover, the filled copper areas help to maintain a low impedance return current path and therefore short current loops. However, do not forget to place a grid of ground stitch vias throughout the whole PCB (otherwise some small copper islands may radiate)! This is very important! Read about the distances between the vias below in Rule Of Thumb #5.
Plated PCB outside edges (which are connected to circuit GND) help to prevent the inner PCB layers from radiating. Moreover, the plated PCB edges help to increase cooling efficiency of a PCB, because there is an additional copper surface where heat exchange can take place. The additional costs for metalized PCB edges are low.
Rule Of Thumb #5: It is best practice to add a grid of ground stitch vias over the whole PCB (when filling top and bottom layers with a ground plane). Otherwise, some small GND copper areas would tend to radiate! The distance between these vias within that grid depends on the highest frequency fmax on the PCB. Given a signal with wavelength λ, it is a rule of thumb that a stub or trace of the length of λ/10 starts to become a problem (regarding radiation) and a trace of length λ/20 won't be a problem (in between λ/10 and λ/20 is a gray area). Therefore, the distance between the vias should be shorter than λ/10 of fmax. The wavelength λ of a sinusoidal signal running through a PCB signal trace is (read the derivation of this formula in our chapter about Frequency and Wavelength):
Where λ = wavelength [m], c = speed of light [3E8 m/sec], f = frequency [Hz] and εr = permeability  of the PCB material (e.g. typical εr=4.5 for FR-4 and e.g. εr=2...11 for special high frequency (f > 2GHz) PCB materials, where an isotropic and stable dielectric constant is needed over a wide frequency-range, temperature-range and every PCB-lot).
But how to determine fknee = fmax or λ/10, respectively? Usually, the highest frequencies occur in digital signals with small rise/fall-time, especially clock signals. A good estimation gives our Rule Of Thumb #3 with:
The following table shows some example values of high frequency digital signals rise/fall-time and its corresponding highest frequency content and λ/10 values (the recommended distance between vias of the grid of vias is <λ/10).
EMC Guideline #9 – Add stitching vias around high-speed signal vias.
Lower radiated emission
This guideline follows directly out of EMC Guideline #2. Imagine the following scenario: a high-speed signal switches planes on a PCB. In order to minimize ground bounce, you have to minimize the return current path. There are these two options, depending on the return current path:
Identical return current reference nets. In case the two planes have the same reference net with the identical electrical potential (e.g. GND), add two or three stitching vias (between the reference planes) close to high-speed signal via. These stitching vias help to keep current loops as small as possible.
Different return current reference reference nets. In case the two reference planes are DC isolated, make sure that the two reference planes are coupled with the lowest impedance possible. This can be achieved with the thinnest possible dielectric layer between them (see the picture below)
EMC Guideline #10 – Connect circuit GND to chassis at IO area.
Lower radiated emission, conducted immunity, ESD
Do not think this guideline is not important, just because it isn’t listed at first place! This guideline is essential! Bound your circuit GND to chassis at the area where your cable leaves/enters the chassis. Connect it with VERY LOW impedance!
It is important that GND and chassis have the same potential at the IO area:
This prevents radiation, as the GND shows a minimum voltage difference to the chassis (earth).
This helps your IO-signal-filters on your PCB (see EMC Guideline #7) being most effective and keeps ESD pulses away from your circuit. Why? Because incoming noise (burst, ESD) from the cable can directly flow back over chassis to earth.
Cabling & Wiring Design
EMC Guideline #11 – Lay cables along chassis (GND/earth).
Lower radiated emission, conducted immunity, ESD
Whenever possible, lay cables along chassis:
Emission: This keeps the electromagnetic field generated by the voltage and current in the cable at a minimum radiation level.
Immunity: This minimizes induced current in the cable and cable shield (assumed that shield is laid on both ends to ground). Reason: loop area for induced currents is minimized.
EMC Guideline #12 – Do NOT use shield as signal conductor for low-frequency signals.
Shield should not be one of the signal conductors for low-frequency signals (e.g sensor signals)! Never! Because of the noise current induced in the ground loop.
Hint #5: This rule does NOT apply for high-frequency signals(!), where the signal return current and the noise current are separated by the skin-effect within the shield (e.g. in a coaxial cable). See Guideline #14.
EMC Guideline #13 – Lay only one end of the cable shield to ground for low-frequency signals.
Increase electric fields immunity
When shielding cables, there usually pops up this question: "Should we ground the cable shield on both ends or only on one end?" It may lead to problems when laying both ends of cable shield to ground for low frequency signals, because balancing current in the shield could lead to interference of signals inside the cable. Here the rule of thumb for low-frequency (<20kHz) signals, find more details here:
Protection against electrical fields (E): lay only one end of the shield to ground (with low-impedance) in order to avoid noise current through the shield (e.g induced by magnetic fields or ground loop currents).
Protection against magnetic fields (H): follow Guideline #15.
If you are only in control of one side of the cable shield (because at the other end of the cable is a device from another manufacturer): lay cable shield to ground / chassis with low inductance (no pigtails, use a 360º shield clamp) or implement Hint #5, but NEVER leave it unconnected!
Hint #6: A good compromise for shielding against low- and high-frequency signals at the same time, while minimizing low-frequency balancing currents:
Lay one side of the cable shield to ground with low inductance and low resistance.
Lay the other side of the cable shield to ground with a resistor (to minimizing balance currents for low-frequency signals) and a parallel capacitor to that resistor (to allow high-frequency signals to flow through the cable shield).
EMC Guideline #14 – Lay both ends of the cable shield to ground for high-frequency signals.
Increase electromagnetic fields immunity, lower magnetic fields emission
When shielding cables, there usually pops up this question: "Should we ground the cable shield on both ends or only on one end?" It is a must to lay both ends of a high-frequency signal cable shield to ground with low inductance (no pigtails, use a 360º shield clamp or the like). Here the rule of thumb for high-frequency (>1MHz) signals, find more details here:
The shield can be used as signal return path for high-frequency signals (because the signal return current and the noise current are separated by the skin-effect (e.g. in a coaxial cable , you can find calculated skin-depth below). The induced noise current in the shield helps to cancel out the magnetic field of the noise source.
To lower the emission of magnetic fields from a signal in a cable, the signal should be shielded and the shield has to be laid on ground on both ends.
Hint #7: Here the skin depth calculated for copper according to the formula:
where f=frequency [Hz], permeability constant μ0=4πE-7[H/m], σ=conductivity of copper 5.96E7[S/m].
EMC Guideline #15 – Minimize loop area of signals in cables.
Increase magnetic fields immunity, lower magnetics field emission
The best way to protect a signal in a cable against magnetic fields is to reduce the loop area: Protection against magnetic fields H: minimize loop area between a signal and it’s return path (e.g. use twisted pair, or use neighbor conductors in flat cables).
Hint #8: Cable shields made out of copper or aluminum do NOT protect the signals within the shielded cable from magnetic fields by its nature. A cable shield does protect against electric fields. Read more details in this book here.